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rev. a information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. a ad8601/ad8602/ad8604 one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700 world wide web site: http://www.analog.com fax: 781/326-8703 ? analog devices, inc., 2000 precision cmos single supply rail-to-rail input/output wideband operational amplifiers features low offset voltage: 500 v max single supply operation: 2.7 v to 6 v low supply current: 750 a/amplifier wide bandwidth: 8 mhz slew rate: 5 v/ s low distortion no phase reversal low input currents unity gain stable applications current sensing barcode scanners pa controls battery-powered instrumentation multipole filters sensors asic input or output amplifier audio general description the ad8601, ad 8602, and ad8604 are single, dual, and quad rail - to-rail input and output single supply amplifiers featuring very low offset voltage and wide signal bandwidth. these amplifiers use a new, patented trimming technique that achieves superior perfor- mance without laser trimming. all are fully specified to operate from 3 v to 5 v single supply. the combination of low offsets, very low input bias currents, and high speed make these amplifiers useful in a wide variety of applica- tions. filters, integrators, diode amplifiers, shunt current sensors, and high impedance sensors all benefit from the combination of performance features. audio and other ac applications benefit from the wide bandwidth and low distortion. for the most cost-sensitive applications the d grades offer this ac performance with lower dc precision at a lower price point. applications for these amplifiers include audio amplification for portable devices, portable phone headsets, bar code scanners, portable instruments, cellular pa controls, and multipole filters. the ability to swing rail-to-rail at both the input and output enables designers to buffer cmos adcs, dacs, asics, and other wide output swing devices in single supply systems. the ad8601, ad8602, and ad8604 are specified over the extended industrial (C40 c to +125 c) temperature ran ge. the ad8601, single, is available in the tiny 5-lead sot-23 package. the ad8602, dual, is available in 8-lead msop and narrow soic surface-mount pack- ages. the ad 8604, quad, is available in 14-lead tssop and narrow soic packages. sot, soic, and tssop versions are available in tape and reel only. 14-lead tssop (ru suffix) 14 13 12 11 10 9 8 1 2 3 4 5 6 7 in a in a v in b in b out b out d in d in d v in c in c out c out a ad8604 14-lead soic (r suffix) 14 13 12 11 10 9 8 1 2 3 4 5 6 7 in a in a v in b in b out b out d in d in d v in c in c out c out a ad8604 functional block diagrams 5-lead sot-23 (rt suffix) 1 2 3 5 4 in v in out a v ad8601 8-lead soic (rm suffix) 1 2 3 4 out a 8 7 6 5 in a in a v out b in b v in b ad8602 8-lead soic (r suffix) 1 2 3 4 8 7 6 5 ad8602 in a v in a out b in b v in b out a
C2C rev. a ad8601/ad8602/ad8604?pecifications electrical characteristics a grade d grade parameter symbol conditions min typ max min typ max unit input characteristics offset voltage (ad8601/ad8602) v os 0 v v cm 1.3 v 80 500 1,100 6,000 v C40 c t a +85 c 700 7,000 v C40 c t a +125 c 1,100 7,000 v 0 v v cm 3 v 1 350 750 1,300 6,000 v C40 c t a +85 c 1,800 7,000 v C40 c t a +125 c 2,100 7,000 v offset voltage (ad8604) v os v cm = 0 v to 1.3 v 80 600 1,100 6,000 v C40 c t a +85 c 800 7,000 v C40 c t a +125 c 1,600 7,000 v v cm = 0 v to 3.0 v 1 350 800 1,300 6,000 v C40 c t a +85 c 2,200 7,000 v C40 c t a +125 c 2,400 7,000 v input bias current i b 0.2 60 0.2 200 pa C40 c t a +85 c 25 100 25 200 pa C40 c t a +125 c 150 1,000 150 1,000 pa input offset current i os 0.1 30 0.1 100 pa C40 c t a +85 c 50 100 pa C40 c t a +125 c 500 500 pa input voltage range 0 3 0 3 v common-mode rejection ratio cmrr v cm = 0 v to 3 v 68 83 52 65 db large signal voltage gain a vo v o = 0.5 v to 2.5 v r l = 2 k ? , v cm = 0 v 30 100 20 60 v/mv offset voltage drift ? v os / ? t22 v/ c output characteristics output voltage high v oh i l = 1.0 ma 2.92 2.95 2.92 2.95 v C40 c t a +125 c 2.88 2.88 v output voltage low v ol i l = 1.0 ma 20 35 20 35 mv C40 c t a +125 c50 50mv output current i out 30 30 ma closed-loop output impedance z out f = 1 mhz, a v = 1 12 12 ? power supply power supply rejection ratio psrr v s = 2.7 v to 5.5 v 67 80 56 72 db supply current/amplifier i sy v o = 0 v 680 1,000 680 1,000 a C40 c t a +125 c 1,300 1,300 a dynamic performance slew rate sr r l = 2 k ? 5.2 5.2 v/ s settling time t s to 0.01% <0.5 <0.5 s gain bandwidth product gbp 8.2 8.2 mhz phase margin o 50 50 degrees noise performance voltage noise density e n f = 1 khz 33 33 nv/ hz e n f = 10 khz 18 18 nv/ hz current noise density i n 0.05 0.05 pa/ hz notes 1 for v cm between 1.3 v and 1.8 v, v os may exceed specified value. specifications subject to change without notice. (v s = 3 v, v cm = v s /2, t a = 25 c unless otherwise noted)
C3C rev. a ad8601/ad8602/ad8604 electrical characteristics a grade d grade parameter symbol conditions min typ max min typ max unit input characteristics offset voltage (ad8601/ad8602) v os 0 v v cm 5 v 80 500 1,300 6,000 v C40 c t a +125 c 1,300 7,000 v offset voltage (ad8604) v os v cm = 0 v to 5 v 80 600 1,300 6,000 v C40 c t a +125 c 1,700 7,000 v input bias current i b 0.2 60 0.2 200 pa C40 c t a +85 c 100 200 pa C40 c t a +125 c 1,000 1,000 pa input offset current i os 0.1 30 0.1 100 pa C40 c t a +85 c 6 50 6 100 pa C40 c t a +125 c 25 500 25 500 pa input voltage range 0 5 0 5 v common-mode rejection ratio cmrr v cm = 0 v to 5 v 74 89 56 67 db large signal voltage gain a vo v o = 0.5 v to 4.5 v 30 80 20 60 v/mv r l = 2 k ? , v cm = 0 v offset voltage drift ? v os / ? t22 v/ c output characteristics output voltage high v oh i l = 1.0 ma 4.925 4.975 4.925 4.975 v i l = 10 ma 4.7 4.77 4.7 4.77 v C40 c t a +125 c 4.6 4.6 v output voltage low v ol i l = 1.0 ma 15 30 15 30 mv i l = 10 ma 125 175 125 175 mv C40 c t a +125 c 250 250 mv output current i out 50 50 ma closed-loop output impedance z out f = 1 mhz, a v = 1 10 10 ? power supply power supply rejection ratio psrr v s = 2.7 v to 5.5 v 67 80 56 72 db supply current/amplifier i sy v o = 0 v 750 1,200 750 1,200 a C40 c t a +125 c 1,500 1,500 a dynamic performance slew rate sr r l = 2 k ? 66v/ s settling time t s to 0.01% < 1.0 < 1.0 s full power bandwidth bwp < 1% distortion 360 360 khz gain bandwidth product gbp 8.4 8.4 mhz phase margin o 55 55 degrees noise performance voltage noise density e n f = 1 khz 33 33 nv/ hz e n f = 10 khz 18 18 nv/ hz current noise density i n f = 1 khz 0.05 0.05 pa/ hz specifications subject to change without notice. (v s = 5.0 v, v cm = v s /2, t a = 25 c unless otherwise noted)
ad8601/ad8602/ad8604 C4C rev. a absolute maximum ratings * supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 v input voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . gnd to v s differential input voltage . . . . . . . . . . . . . . . . . . . . . . . . 6 v storage temperature range r, rm, rt, ru packages . . . . . . . . . . . . C65 c to +150 c operating temperature range ad8601/ad8602/ad8604 . . . . . . . . . . . C40 c to +125 c junction temperature range r, rm, rt, ru packages . . . . . . . . . . . . C65 c to +150 c lead temperature range (soldering, 60 sec) . . . . . . . . 300 c esd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 kv hbm * stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those listed in the operational sections of this specification is not implied. exposure to absolute maximum rating condi- tions for extended periods may affect device reliability. package type ja * jc unit 5-lead sot-23 (rt) 230 92 c/w 8-lead soic (r) 158 43 c/w 8-lead msop (rm) 210 45 c/w 14-lead soic (r) 120 36 c/w 14-lead tssop (ru) 180 35 c/w * ja is specified for worst-case conditions, i.e., ja is specified for device in socket for pdip packages; ja is specified for device soldered onto a circuit board for surface mount packages. caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the ad8601/ad8602/ad8604 features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. warning! esd sensitive device ordering guide temperature package package branding model range description option information ad8601art C40 c to +125 c 5-lead sot-23 rt-5 aaa ad8601drt C40 c to +125 c 5-lead sot-23 rt-5 aad ad8602ar C40 c to +125 c 8-lead soic so-8 ad8602dr C40 c to +125 c 8-lead soic so-8 ad8602arm C40 c to +125 c 8-lead msop rm-8 aba ad8602drm C40 c to +125 c 8-lead msop rm-8 abd AD8604AR C40 c to +125 c 14-lead soic r-14 ad8604dr C40 c to +125 c 14-lead soic r-14 AD8604ARu C40 c to +125 c 14-lead tssop ru-14 ad8604dru C40 c to +125 c 14-lead tssop ru-14
ad8601/ad8602/ad8604 C5C rev. a typical performance characteristics input offset voltage ?mv 3,000 1,500 0 1.0 1.0 0.8 quantity ?amplifiers 0.6 0.4 0.2 0 0.2 0.4 0.6 0.8 2,500 2,000 1,000 500 v s = 3v t a = 25 c v cm = 0v to 3v tpc 1. input offset voltage distribution input offset voltage mv 3,000 1,500 0 1.0 1.0 0.8 quantity amplifiers 0.6 0.4 0.2 0 0.2 0.4 0.6 0.8 2,500 2,000 1,000 500 v s = 5v t a = 25 c v cm = 0v to 5v tpc 2. input offset voltage distribution tcvos v/ c 60 30 0 010 1 quantity amplifiers 23456789 50 40 20 10 v s = 3v t a = 25 c to 85 c tpc 3. input offset voltage drift distribution tcvos v/ c 60 30 0 010 1 quantity amplifiers 23456789 50 40 20 10 v s = 5v t a = 25 c to 85 c '()$ +

common-mode voltage v 1.5 2.0 03.0 0.5 input offset voltage mv 1.0 1.5 2.0 2.5 1.0 0.5 0 1.0 1.5 0.5 v s = 3v t a = 25 c tpc 5. input offset voltage vs. common-mode voltage common-mode voltage v 1.5 2.0 01 input offset voltage mv 2345 1.0 0.5 0 1.0 1.5 0.5 v s = 5v t a = 25 c tpc 6. input offset voltage vs. common-mode voltage
ad8601/ad8602/ad8604 C6C rev. a 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 300 250 0 input bias current pa 200 150 100 50 v s = 3v tpc 7. input bias current vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 300 250 0 input bias current pa 200 150 100 50 v s = 5v tpc 8. input bias current vs. temperature common-mode voltage v 5 0 4.0 input bias current pa 2.0 2.5 3.0 3.5 2 1 3 v s = 5v t a = 25 c 4 0 0.5 1.0 1.5 4.5 5.0 tpc 9. input bias current vs. common-mode voltage 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 30 25 0 input offset current pa 20 15 10 5 v s = 3v tpc 10. input offset current vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 30 25 0 input offset current pa 20 15 10 5 v s = 5v tpc 11. input offset current vs. temperature load current ma 10k 10 0.1 0.001 100 0.01 output voltage mv 0.1 1 10 1 100 source sink 1k v s = 2.7v t a = 25 c tpc 12. output voltage to supply rail vs. load current
ad8601/ad8602/ad8604 C7C rev. a load current ma 10k 10 0.1 0.001 100 0.01 output voltage mv 0.1 1 10 1 100 source sink 1k v s = 5v t a = 25 c tpc 13. output voltage to supply rail vs. load current 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 5.1 5.0 4.5 output voltage v 4.9 4.8 4.7 4.6 v s = 5v v oh @ 1ma load v oh @ 10ma load tpc 14. output voltage swing vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 250 0 output voltage mv 200 150 100 50 v ol @ 10ma load v s = 5v v ol @ 1ma load tpc 15. output voltage swing vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 35 30 0 output voltage mv 20 15 5 v ol @ 1ma load v s = 2.7v 10 25 tpc 16. output voltage swing vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 2.67 2.66 2.62 output voltage v 2.64 v oh @ 1ma load v s = 2.7v 2.63 2.65 tpc 17. output voltage swing vs. temperature frequency hz 1k 100m 10k gain db 100k 1m 10m 80 60 40 20 0 45 90 135 180 phase shift degrees v s = 3v r l = no load t a = 25 c 100 20 40 60 tpc 18. open-loop gain and phase vs. frequency
ad8601/ad8602/ad8604 C8C rev. a frequency hz 1k 100m 10k gain db 100k 1m 10m 80 60 40 20 0 45 90 135 180 phase shift degrees v s = 5v r l = no load t a = 25 c 100 20 40 60 tpc 19. open-loop gain and phase vs. frequency frequency hz 1k 100m 10k closed-loop gain db 100k 1m 10m 40 20 0 v s = 3v t a = 25 c a v = 100 a v = 10 a v = 1 tpc 20. closed-loop gain vs. frequency frequency hz 1k 100m 10k closed-loop gain db 100k 1m 10m 40 20 0 v s = 5v t a = 25 c a v = 100 a v = 10 a v = 1 tpc 21. closed-loop gain vs. frequency frequency hz 3.0 2.5 0 1k 10m 10k output swing v p-p 100k 1m 2.0 0.5 1.5 1.0 v s = 2.7v v in = 2.6v p-p r l = 2k t a = 25 c a v = 1 tpc 22. closed-loop output voltage swing vs. frequency frequency hz 6 5 0 1k 10m 10k output swing v p-p 100k 1m 4 1 3 2 v s = 5v v in = 4.9v p-p r l = 2k t a = 25 c a v = 1 tpc 23. closed-loop output voltage swing vs. frequency frequency hz 100 10m 1k output impedance 10k 100k 1m 160 120 80 v s = 3v t a = 25 c a v = 100 a v = 10 a v = 1 0 20 40 60 100 140 180 200 tpc 24. output impedance vs. frequency
ad8601/ad8602/ad8604 C9C rev. a frequency hz 100 10m 1k output impedance 10k 100k 1m 160 120 80 v s = 5v t a = 25 c a v = 100 a v = 10 a v = 1 0 20 40 60 100 140 180 200 tpc 25. output impedance vs. frequency frequency hz 1k 20m 10k common-mode rejection db 100k 1m 160 140 40 120 100 80 60 40 20 0 20 10m v s = 3v t a = 25 c tpc 26. common-mode rejection ratio vs. frequency frequency hz 1k 20m 10k common-mode rejection db 100k 1m 160 140 40 120 100 80 60 40 20 0 20 10m v s = 5v t a = 25 c tpc 27. common-mode rejection ratio vs. frequency frequency hz 100 10m 1k power supply rejection db 10k 100k 1m 120 80 40 v s = 5v t a = 25 c 40 20 0 20 60 100 140 160 '()"1 (
49 7
8 v s = 2.7v r l = t a = 25 c a v = 1 capacitance pf 70 60 0 10 1k 100 small signal overshoot % 50 40 30 20 10 os +os tpc 29. small signal overshoot vs. load capacitance v s = 5v r l = t a = 25 c a v = 1 capacitance pf 70 60 0 10 1k 100 small signal overshoot % 50 40 30 20 10 os +os tpc 30. small signal overshoot vs. load capacitance
ad8601/ad8602/ad8604 C10C rev. a 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 1.2 1.0 0 supply current per amplifier ma 0.8 0.6 0.4 0.2 v s = 5v tpc 31. supply current per amplifier vs. temperature 40 125 20 65 25 10 5 35 50 80 95 110 temperature c 1.0 0.8 0 supply current per amplifier ma 0.6 0.4 0.2 v s = 3v tpc 32. supply current per amplifier vs. temperature supply voltage v 0.8 0 supply current per amplifier ma 0.7 0.4 0.3 0.2 0.1 0.6 0.5 0 6 12345 tpc 33. supply current per amplifier vs. supply voltage fre q uency hz 0.1 0.0001 thd + n % 0.001 0.01 20 20k 100 1k 10k v s = 5v t a = 25 c r l = 600 r l = 2k r l = 10k r l = 10k r l = 2k r l = 600 g = 10 g = 1 tpc 34. total harmonic distortion + noise vs. frequency v s = 2.7v t a = 25 c frequency khz 0 0 5 10 15 20 25 voltage noise density nv/ hz 8 16 24 32 40 48 56 64 tpc 35. voltage noise density vs. frequency v s = 2.7v t a = 25 c frequency khz 0 0 0.5 1.0 1.5 2.0 2.5 26 52 78 104 130 156 182 208 voltage noise density nv/ hz tpc 36. voltage noise density vs. frequency
ad8601/ad8602/ad8604 C11C rev. a v s = 5v t a = 25 c frequency khz 0 0 0.5 1.0 1.5 2.0 2.5 26 52 78 104 130 156 182 208 voltage noise density nv/ hz tpc 37. voltage noise density vs. frequency v s = 5v t a = 25 c frequency khz 0 0 5 10 15 20 25 8 16 24 32 40 48 56 64 voltage noise density nv/ hz tpc 38. voltage noise density vs. frequency v s = 5v t a = 25 c frequency khz 0 0 0.5 1.0 1.5 2.0 2.5 26 52 78 104 130 156 182 208 voltage noise density nv/ hz tpc 39. 0.1 hz to 10 hz input voltage noise voltage 2.5 v/div time 1s/div v s = 5v t a = 25 c tpc 40. 0.1 hz to 10 hz input voltage noise 50.0mv/div 200ns/div v s = 5v r l = 10k c l = 200pf t a = 25 c tpc 41. small signal transient response 50.0mv/div 200ns/div v s = 2.7v r l = 10k c l = 200pf t a = 25 c tpc 42. small signal transient response
ad8601/ad8602/ad8604 C12C rev. a voltage 1.0v/div time 400ns/div v s = 5v r l = 10k c l = 200pf a v = 1 t a = 25 c tpc 43. large signal transient response voltage 500mv/div time 400ns/div v s = 2.7v r l = 10k c l = 200pf a v = 1 t a = 25 c tpc 44. large signal transient response voltage 1v/div time 2.0 s/div v s = 2.7v r l = 10k a v = 1 t a = 25 c v in v out tpc 45. no phase reversal voltage 1v/div time 2.0 s/div v s = 5v r l = 10k a v = 1 t a = 25 c v in v out tpc 46. no phase reversal voltage v time 100ns/div +0.1% error v out 0.1% error v in v in trace 0.5v/div v out trace 10mv/div v s = 5v r l = 10k v o = 2v p-p t a = 25 c tpc 47. settling time settling time ns 2.0 2.0 output swing v 1.5 0 0.5 1.0 1.5 1.0 0.5 300 600 350 400 450 500 550 0.1% 0.01% 0.01% 0.1% v s = 2.7v t a = 25 c tpc 48. output swing vs. settling time
ad8601/ad8602/ad8604 C13C rev. a settling time ns 5 5 output swing v 3 0 1 3 4 2 1 0 1,000 200 400 600 800 0.1% 0.01% 0.01% 0.1% 2 4 v s = 5v t a = 25 c tpc 49. output swing vs. settling time theory of operation the ad8601/ad8602/ad8604 family of amplifiers are rail-to-rail input and output precision cmos amplifiers that operate from 2.7 v to 5.0 v of power supply voltage. these amplifiers use analog devices proprietary technology called digitrim? to achieve a higher deg ree of precision than avail able from most cmos amplifiers. digitrim technology is a method of trimming the offset voltage of the amplifier after it has already been assembled. the advantage in post-package trimming lies in the fact that it corrects any offset voltages due to the mechanical stresses of assembly. this tech nology is scalable and utilized with every package option, including sot23-5, providing lower offset voltages than previously achieved in these small packages. the digitrim process is done at the factory and does not add additional pins to the amplifier. all ad860x amplifiers are avail- able in standard op amp pinouts, making digitrim completely transparent to the user. the ad860x can be used in any preci- sion op amp application. the input stage of the amplifier is a true rail-to-rail architecture, allowing the input common-mode voltage range of the op amp to extend to both positive and negative supply rails. the voltage swing of the output stage is also rail-to-rail and is achieved by using an nmos and pmos transistor pair connected in a common-source configuration. the maximum output voltage swing is proportional to the output current, and larger currents will limit how close the output voltage can get to the supply rail. this is a characteristic of all rail-to-rail output amplifiers. with 1 ma of output current, the output voltage can reach within 20 mv of the positive rail and 15 mv of the negative rail. at light loads of >100 k ? , the output swings within ~1 mv of the supplies. the open-loop gain of the ad860x is 80 db, typical, with a load of 2 k ? . because of the rail-to-rail output configuration, the gain of the output stage, and thus the open-loop gain of the amplifier, is dependent on the load resistance. open-loop gain will decrease with smaller load resistances. again, this is a characteristic inher- ent to all rail-to-rail output amplifiers. rail-to-rail input stage the input common-mode voltage range of the ad860x extends to both positive and negative supply voltages. this maximizes the usable voltage range of the amplifier, an important feature for single supply and low voltage applications. this rail-to-rail input range is achieved by using two input differential pairs, one nmos and one pmos, placed in parallel. the nmos pair is active at the upper end of the common-mode voltage range, and the pmos pair is active at the lower end of the common-mode range. the nmos and pmos input stage are separately trimmed using digitrim to minimize the offset voltage in both differential pairs. both nmos and pmos input differential pairs are active in a 500 mv transition region, when the input common-mode voltage is between approximately 1.5 v and 1 v below the positive supply voltage. input offset voltage will shift slightly in this transition region, as shown in figures 5 and 6. common-mode rejection ratio will also be slightly lower when the input common-mode voltage is within this transition band. compared to the burr brown opa2340 rail-to-rail input amplifier, shown in figure 1, the ad860x, shown in figure 2, exhibits lower offset voltage shift across the entire input common-mode range, including the transi- tion region. v cm v 0.7 0.4 1.4 0 5 1 v os mv 234 0.2 0.5 0.8 1.1 0.1 figure 1. burr brown opa2340ur input offset voltage vs. common-mode voltage, 24 soic units @ 25 c v cm v 0.7 0.4 1.4 0 5 1 v os mv 234 0.2 0.5 0.8 1.1 0.1 figure 2. ad8602ar input offset voltage vs. common-mode voltage, 300 soic units @ 25 c digitrim is a trademark of analog devices.
ad8601/ad8602/ad8604 C14C rev. a input overvoltage protection as with any semiconductor device, if a condition could exist for the input voltage to exceed the power supply, the devices input overvoltage characteristic must be considered. excess input voltage will energize internal pn junctions in the ad860x, allowing current to flow from the input to the supplies. this input current will not damage the amplifier provided it is limited to 5 ma or less. this can be ensured by placing a resistor in series with the input. for example, if the input voltage could exceed the supply by 5 v, the series resistor should be at least (5 v/5 ma) = 1 k ? . with the input voltage within the supply rails, a minimal amount of current is drawn into the inputs which, in turn, causes a negligible voltage drop across the series resistor. thus, adding the series resistor will not adversely affect circuit performance. overdrive recovery overdrive recovery is defined as the time it takes the output of an amplifier to come off the supply rail when recovering from an over- load signal. this is tested by placing the amplifier in a closed-loop gain of 10 with an input square wave of 2 v peak-to-peak while the amplifier is powered from either 5 v or 3 v. the ad860x has excellent recovery time from overload conditions. the output recovers from the positive supply rail within 200 ns at all supply voltages. recovery from the negative rail is within 500 ns at 5 v supply, decreasing to within 350 ns when the device is powered from 2.7 v. power-on time power-on time is important in portable applications, where the supply voltage to the amplifier may be toggled to shut down the device to improve battery life. fast power-up behavior ensures the output of the amplifier will quickly settle to its final voltage, thus improving the power-up speed of the entire system. once the supply voltage reaches a minimum of 2.5 v, the ad860x will settle to a valid output within 1 s. this turn-on response time is faster than many other precision amplifiers, which can take tens or hundreds of microseconds for their output to settle. using the ad8602 in high source impedance applications the cmos rail-to-rail input structure of the ad860x allows these amplifiers to have very low input bias currents, typically 0.2 pa. this allows the ad860x to be used in any application that has a high source impedance or must use large value resistances around the amplifier. for example, the photodiode amplifier circuit shown in figure 3 requires a low input bias current op amp to reduce output voltage error. the ad8601 minimizes offset errors due to its low input bias current and low offset voltage. the current through the photodiode is proportional to the incident light power on its surface. the 4.7 m ? resistor converts this current into a voltage, with the output of the ad8601 increas- ing at 4.7 v/ a. the feedback capacitor reduces excess noise at higher frequencies by limiting the bandwidth of the circuit to: bw mc f = ? () 1 247 . (1) using a 10 pf feedback capacitor limits the bandwidth to approxi- mately 3.3 khz. 4.7m 10pf (optional) d1 v out 4.7v/ a ad8601 figure 3. amplifier photodiode circuit high- and low-side precision current monitoring because of its low input bias current and low offset voltage, the ad860x can be used for precision current monitoring. the true rail-to-rail input feature of the ad860x allows the amplifier to monitor current on either high-side or low-side. using both amplifiers in an ad8602 provides a simple method for monitoring both current supply and return paths for load or fault detection. figure 4 and 5 demonstrate both circuits. 3v return to ground 1/2 ad8602 3v r2 2.49k monitor output r1 100 r sense 0.1 q1 2n3905 figure 4. a low-side current monitor 3v 0.1 f r sense 0.1 v+ i l q1 2n3904 monitor output 3v r2 2.49k r1 100 1/2 ad8602 figure 5. a high-side current monitor voltage drop is created across the 0.1 ? resistor that is propor- tional to the load current. this voltage appears at the inverting input of the amplifier due to the feedback correction around the op amp. this creates a current through r1 which, in turn, pulls current through r2. for the low side monitor, the monitor output voltage is given by: monitor output r r r i sense l = ? ? ? ? ? ? 2 1 (2) for the high-side monitor, the monitor output voltage is:
ad8601/ad8602/ad8604 C15C rev. a monitor output v r r r i sense l =+? () ? ? ? ? ? ? 2 1 (3) using the components shown, the monitor output transfer function is 2.5 v/a. using the ad8601 in single supply mixed-signal applications single supply mixed-signal applications requiring 10 or more bits of resolution demand both a minimum of distortion and a maximum range of voltage swing to optimize performance. to ensure the a/d or d/a converters achieve their best performance an amplifier often must be used for buffering or signal conditioning. the 750 v maximum offset voltage of the ad8601 allows the amplifier to be used in 12-bit applications powered from a 3 v single supply, and its rail-to-rail input and output ensure no signal clipping. figure 6 shows the ad8601 used as a input buffer amplifier to the ad7476, a 12-bit 1 mhz a/d converter. as with most a/d converters, total harmonic distortion (thd) increases with higher source impedances. by using the ad8601 in a buffer configura- tion, the low output impedance of the amplifier minimizes thd while the high input impedance and low bias current of the op amp minimizes errors due to source impedance. the 8 mhz gain-bandwidth product of the ad8601 ensures no signal attenu- ation up to 500 khz, which is the maximum nyquist frequency for the ad7476. sclk c/ p v in r s 3 4 5 1 2 ad8601 sdata cs v in gnd ad7476/ad7477 serial interface 5v supply 0.1 f 10 f ref193 0.1 f 1 f tant v dd 3v 680nf figure 6. a complete 3 v 12-bit 1 mhz a/d conversion system figure 7 demonstrates how the ad8601 can be used as an output buffer for the dac for driving heavy resistive loads. the ad5320 is a 12-bit d/a converter that can be used with clock frequencies up to 30 mhz and signal frequencies up to 930 khz. the rail-to- rail output of the ad8601 allows it to swing within 100 mv of the positive supply rail while sourcing 1 ma of current. the total current drawn from the circuit is less than 1 ma, or 3 mw from a 3 v single supply. 3 4 5 1 2 ad8601 r l v out 0v to 3.0v ad5320 2 1 3v 1 f 3-wire serial interface 4 5 6 figure 7. using the ad8601 as a dac output buffer to drive heavy loads the ad8601, ad7476, and ad5320 are all available in space- saving sot-23 packages. pc100 compliance for computer audio applications because of its low distortion and rail-to-rail input and output, the ad860x is an excellent choice for low cost, single supply audio applications, ranging from microphone amplification to line output buffering. tpc 34 shows the total harmonic distortion plus noise (thd + n) figures for the ad860x. in unity gain, the amplifier has a typical thd + n of 0.004%, or C86 db, even with a load resistance of 600 ? . this is compliant with the pc100 specification requirements for audio in both portable and desktop computers. figure 8 shows how an ad8602 can be interfaced with an ac97 codec to drive the line output. here, the ad8602 is used as a unity-gain buffer from the left and right outputs of the ac97 codec. the 100 f output coupling capacitors block dc current and the 20 ? series resistors protect the amplifier from short-circuits at the jack. u1-a r2 2k 4 c1 100 f 5v 1 8 2 3 5v v dd v dd left out ad1881 (ac'97) right out v ss r4 20 5 6 7 r5 20 c2 100 f note: additional pins omitted for clarity u1-b u1 = ad8602d r3 2k 28 35 36 figure 8. a pc100 compliant line output amplifier spice model the spice macro-model for the ad860x amplifier is available and can be downloaded from the analog devices website at http://www.analog.com . the model will accurately simulate a number of both dc and ac parameters, including open-loop gain, bandwidth, phase margin, input voltage range, output voltage swing versus output current, slew rate, input voltage noise, cmrr, psrr, and supply current versus supply voltage. the model is optimized for performance at 27 c. although it will function at different temperatures, it may lose accuracy with respect to the actual behavior of the ad860x.
C16C rev. a c01525C0C10/00 (rev. a) printed in u.s.a. ad8601/ad8602/ad8604 outline dimensions dimensions shown in inches and (mm). 5-lead sot-23 (rt suffix) 1 3 2 54 0.1220 (3.100) 0.1063 (2.700) pin 1 0.0709 (1.800) 0.0590 (1.500) 0.1181 (3.000) 0.0984 (2.500) 0.0748 (1.900) ref 0.0374 (0.950) ref 0.0197 (0.500) 0.0118 (0.300) 0.0512 (1.300) 0.0354 (0.900) seating plane 0.0571 (1.450) 0.0354 (0.900) 0.0059 (0.150) 0.0000 (0.000) 0.0079 (0.200) 0.0035 (0.090) 0.0236 (0.600) 0.0039 (0.100) 10 0 8-lead soic (so suffix) 0.1968 (5.00) 0.1890 (4.80) 85 4 1 0.2440 (6.20) 0.2284 (5.80) pin 1 0.1574 (4.00) 0.1497 (3.80) 0.0688 (1.75) 0.0532 (1.35) seating plane 0.0098 (0.25) 0.0040 (0.10) 0.0192 (0.49) 0.0138 (0.35) 0.0500 (1.27) bsc 0.0098 (0.25) 0.0075 (0.19) 0.0500 (1.27) 0.0160 (0.41) 8 0 0.0196 (0.50) 0.0099 (0.25) x 45 8-lead soic (rm suffix) 85 4 1 0.122 (3.10) 0.114 (2.90) 0.199 (5.05) 0.187 (4.75) pin 1 0.0256 (0.65) bsc 0.122 (3.10) 0.114 (2.90) seating plane 0.006 (0.15) 0.002 (0.05) 0.018 (0.46) 0.008 (0.20) 0.043 (1.09) 0.037 (0.94) 0.120 (3.05) 0.112 (2.84) 0.011 (0.28) 0.003 (0.08) 0.028 (0.71) 0.016 (0.41) 33 27 0.120 (3.05) 0.112 (2.84) 14-lead soic (r suffix) 14 8 7 1 0.2440 (6.20) 0.2284 (5.80) 0.1574 (4.00) 0.1497 (3.80) pin 1 0.3444 (8.75) 0.3367 (8.55) 0.050 (1.27) bsc seating plane 0.0098 (0.25) 0.0040 (0.10) 0.0192 (0.49) 0.0138 (0.35) 0.0688 (1.75) 0.0532 (1.35) 8 0 0.0196 (0.50) 0.0099 (0.25) 45 0.0500 (1.27) 0.0160 (0.41) 0.0099 (0.25) 0.0075 (0.19) 14-lead tssop (ru suffix) 14 8 7 1 0.256 (6.50) 0.246 (6.25) 0.177 (4.50) 0.169 (4.30) pin 1 0.201 (5.10) 0.193 (4.90) seating plane 0.006 (0.15) 0.002 (0.05) 0.0118 (0.30) 0.0075 (0.19) 0.0256 (0.65) bsc 0.0433 (1.10) max 0.0079 (0.20) 0.0035 (0.090) 0.028 (0.70) 0.020 (0.50) 8 0

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